Built-in test for high speed electrical networks

ABSTRACT

An apparatus for providing auxiliary signals on a high speed electrical signal network is provided such that the auxiliary signals may be used for independent monitoring or communication of monitored information without affecting data or bit error rates for the primary high speed data signals. The auxiliary signals may be used as part of a built-in testing of a network, including electrical time-domain reflectometry measurements to determine fault locations in a network.

FIELD OF THE INVENTION

The present disclosure relates to apparatuses and techniques forcommunicating signals on an electrical network and, more particularly,to apparatuses and techniques for communicating diagnostic information.

BACKGROUND OF THE RELATED ART

Although optical networks are being deployed in military and commercialapplications with increasing regularity, electrical signal networks arestill in wide use, as they can provide low-cost, more robust solutionsdepending on the application. Plus, although optical networkstheoretically offer higher bandwidth, electrical networks are capable ofoperating over large enough bandwidth regions to satisfy manyapplications.

As with optical networks, it is desirable in electrical networks tomaintain signal integrity throughout the network, which means reducingsignal losses at each node, at each device, and on the electrical linescoupled between nodes and devices. To ensure network integrity,designers and maintenance personnel use network analyzing equipment toidentify faults in an electrical network. Typically, such analysisrequires that technicians physically examine different portions of thenetwork with analyzing equipment until the fault is identified—a timeconsuming process. To expedite analysis, there is a need for built intesting within network devices, e.g., transceivers, so that devicesthemselves are able to monitor their operating conditions and/or theoperating conditions of other devices on the network. This networkself-diagnosis would greatly reduce the time spent by technicians intrying to isolate faults.

Despite the need for built in testing capability, in many applicationsincluding aerospace applications, space constraints and costs limit adesigner's ability to make devices with proper testing capability. It istherefore desirable to have techniques for obtaining diagnosticinformation using existing network components and without substantiallyinterfering with the existing network devices or appreciably increasingnetwork size, cost, or complexity.

SUMMARY OF THE INVENTION

In an embodiment provided is an apparatus for providing auxiliarychannel communication on an electrical signal-based network, theapparatus comprising: an electrical signal source adapted to provide ahigh-speed data signal extending over a high frequency range and havinga first maximum peak-to-peak value, the signal source adapted to providean auxiliary data signal extending over a low frequency range below thehigh frequency range and having a second maximum peak-to-peak valuesmaller than the first maximum peak-to-peak value, where the secondmaximum peak-to-peak value is at least two orders of magnitude smallerthe first maximum peak-to-peak value; and a controller coupled to thesignal source for controlling the signal source to produce thehigh-speed data signal and for modulating the high-speed data signalwith the auxiliary data signal.

Another embodiment provides an apparatus for testing an electricalsignal-based network capable of transmitting a high-speed data signalextending over a high frequency range and having a first maximumpeak-to-peak value, the apparatus comprising: a transmitter having asignal source adapted to modulate the high-speed data signal with anauxiliary data signal extending over a low frequency range below thehigh frequency range and having a second maximum peak-to-peak value,where the second maximum peak-to-peak value is at least two orders ofmagnitude smaller than the first maximum peak-to-peak value, theauxiliary data signal comprising operational data of the transmitter;and an analyzing circuit coupled to receive the modulated high-speeddata signal from the signal source and adapted to separately analyze theauxiliary data signal from the modulated high-speed data signal forassessing the operational data.

Yet another embodiment provides an apparatus for performing electricaltime-domain reflectometry on an electrical network having a transmissionline, the apparatus comprising: an output stage comprising an electricalsignal source adapted to provide a high-speed data signal extending overa high frequency range and having a first maximum peak-to-peak value,the signal source adapted to provide an auxiliary data signal extendingover a low frequency range below the high frequency range and having asecond maximum peak-to-peak value smaller than the first maximumpeak-to-peak value, where the second maximum peak-to-peak value is atleast two orders of magnitude smaller the first maximum peak-to-peakvalue, and comprising a controller coupled to the signal source forcontrolling the signal source to produce the high-speed data signal andfor modulating the high-speed data signal with the auxiliary datasignal; and a testing stage for sending a test signal on thetransmission line and comprising a receiver coupled to receive areflected portion of the test signal, the receiver comprising, asample-and-hold device adapted to store the reflected portion, and avariable delay device coupled to the sample-and-hold device forcontrolling a timing interval of said storage.

Another embodiment provides a method for testing an electricalsignal-based network capable of transmitting a high-speed data signalextending over a high frequency range and having a first maximumpeak-to-peak value, the method comprising: adapting a signal source tomodulate the high-speed data signal with an auxiliary data signalextending over a low frequency range below the high frequency range andhaving a second maximum peak-to-peak value, where the second maximumpeak-to-peak value is at least two orders of magnitude smaller than thefirst maximum peak-to-peak value, the auxiliary data signal comprisingoperational data of the transmitter; and providing an analyzing circuitadapted to separately analyze the auxiliary data signal from themodulated high-speed data signal for assessing the operational data.

The features, functions, and advantages can be achieved independently invarious embodiments of the present invention or may be combined in yetother embodiments.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates an example electrical network providing a transmitterand a receiver capable of communicating high speed data signals and lowspeed data signals simultaneously.

FIG. 2 illustrates an example circuit level implementation of anauxiliary signal recovery stage of FIG. 1.

FIG. 3 provides a graph of an example spectral distribution of ahigh-speed data signal and a lower speed auxiliary data signal as may becombined for communication in the apparatus of FIG. 1.

FIGS. 4A and 4B illustrate a high-speed data signal, in the form of aManchester signal and a lower speed auxiliary data signal and amodulated version of the two, respectively.

FIGS. 5A-5C illustrate the modulated high-speed data signal of FIG. 4B,a rectification of an auxiliary data signal from that modulatedhigh-speed data signal, and a low band pass filtered version of thatrectified signal, respectively, the latter of which illustrates a highsignal-to-noise, low frequency auxiliary data signal having beeneffectively removed from the modulated high-speed data signal.

FIG. 6 illustrates an example built-in test system having a time-domainreflectometry mode and an auxiliary modulated high-speed data signalmode.

DETAILED DESCRIPTION OF AN EXAMPLE

The data signal format in many high-speed networks such as GigabitEthernet, Fibre Channel, IEEE-1394b, Infiniband, RapidIO, and others iscalled 8B10B, binary-level. With the 8B10B format, energy isconcentrated at high frequencies, and long run-lengths are prohibited by8B10B. For example, in some networks virtually no energy will appearbelow a low frequency threshold, e.g., 10 MHz in an 8B10B format. As aresult, it is possible to modulate the high speed data signals with alow-frequency signal that includes operational data of a device ornetwork, such as health information obtained by a diagnostic system orbuilt-in test system. Various examples are described below fortransmitting health information data or other auxiliary data as acarrier on a high speed data signal and for removing that healthinformation data from the high speed data signal while maintaining highsignal-to-noise ratios and frequency isolation. In some examples, theintensity of the modulating wave may be orders of magnitude smaller thanthe intensity of the high speed data signal; therefore, the integrity ofthe high-speed data signal will not be compromised by the modulation.The frequency ranges for modulating waves and the high speed data signalmay be set to different, non-overlapping regions in some examples forisolating the signals. Yet, while examples are described below inparticular applications, it will be appreciated that the presentinvention is not limited to the examples described. And it will beappreciated that the examples are provided for explanation purpose, notlimitation. Indeed, various modifications, substitutions, andalterations will be appreciated from reading the disclosure.

FIG. 1 illustrates an example network 100 having both a transmitter 102and a receiver 104, which may represent different devices on anelectrical transmission line 106, such as a copper wire. Alternatively,the example network 100 may represent two parts of a single transceivercoupled to the transmission line 106. Example high speed data networksinclude Gigabit Ethernet, Fibre Channel, IEEE-1394b, and Infiniband,although it will be appreciated that the examples provided herein arenot limited to a particular network type, data format, or datatransmission rate. In preferred examples, the network 100 transmitshigh-speed data signals over a particular high frequency bandwidth rangeleaving unused a complementary low frequency bandwidth that may be usedto transmit lower data rate signals, such as auxiliary data, an exampleof which is the 8B10B signal format.

In the illustrated example, the transmitter 102 includes an electricalsignal source 108 that provides a main network data signal source 110and an auxiliary data signal source 112, where the main data signal mayrepresent high-speed data signals and the auxiliary data signal mayrepresent low speed operational data, such as health information fromdiagnostic or other built-in test data. The signal sources arecontrolled by a processor 111. In the illustrated example, an optionalbuilt-in tester 113 is shown coupled to the source 108 to provide theauxiliary data for the signal source. By way of example, built-in testsmay monitor transmitter power, detector signal current, power supplyvoltage, power supply current, transmitter temperature, average casetemperature, time-domain reflectometry (TDR) measurements or othermetrics. An example TDR implementation is illustrated in FIG. 6.

The main and auxiliary data signals are provided to a combining circuit114 coupled to the signal source 108 for controlling the signal source108 to produce a combined signal of the main data signal and auxiliarydata signal on the transmission line 106. For example, the combiningcircuit 114 may be a mixer capable of combining the signals by forexample modulating the main data signal with the lower speed auxiliarydata signal. In the illustrated example, the combining circuit 114 iscoupled to an optional transmitter 116 that transmits the combinedsignal on the transmission line 106, where the transmitter 116 mayrepresent a gain stage with or without additional modulation or signalshaping. It will be appreciated by persons of ordinary skill in the artthat although the combining circuit 114, transmitter 116 and theelectrical signal source 108 are illustrated as separate elements, thesecircuit devices may be combined, substituted, or modified as desired.

The receiver 104 is also coupled to the transmission line 106 and in theillustrated example includes a splitter element 118 coupled to a maindata signal stage 120 and an auxiliary data stage 122, for example toprovide identical 3 dB signals V_(B) and V_(A), respectively. Theauxiliary data stage 122, includes a rectifier 124 for removing aportion of the voltage of the combined signal originally sent fromcircuit 114 and for providing that rectified signal to a band-passfiltering/low noise amplifier circuit 126 capable of removing highfrequencies from the rectified combined signal including the high-speeddata from the main data signal source 110. That is, the auxiliary datastage 122 is capable of removing the modulating auxiliary signal, eitherin an analog circuit or a digital circuit, in a way in which datatransmitted on that signal may be decoded without having the high speeddata signal affect the accuracy of that decoding. Although the detailsof the main data stage 120 are not described, it will be appreciatedthat this data stage may include similar device elements to those ofstage 122, although if the main data signal is a high speed data signalthen demodulating/decoding circuitry may be used without needing to passthe signal through a potentially lossy high frequency band pass filter;as the modulating auxiliary wave may be of sufficiently low frequencyand sufficiently low intensity so as to be undetected by thedemodulating/decoding circuit, and thus leave the high-speed data signalsubstantially unaffected.

In the illustrated example, the main data signal from the stage 120 andthe auxiliary data signal (V_(AUX)) from the stage 122 are both providedto a microprocessor 128 that decodes the data (e.g., bit information)contained in each. The processor 128, for example, decodes the auxiliarydata signal to determine health information or built-in test data fromthe transmitter 102, as measured by device 113. In other examples, theauxiliary data signal may contain instructions for the receiver 104 toperform its own built-in test using test equipment coupled to themicroprocessor 128 (not shown).

FIG. 2 illustrates an example implementation of the auxiliary stage 122,in which rectification is achieved by a diode rectifier 124 andfiltering by a low frequency bandpass filter 126 comprising a resistor123 and a capacitor 125. A gain stage amplifier is coupled to the filterand produces the output auxiliary signal, V_(AUX). It will beappreciated that the illustrated stage is an example and thatrectification and filtering may be achieved in different ways, withanalog or digital circuitry, and in a different order than illustrated.

FIG. 3 is a graph of a spectral distribution 300 of a combined signalfrom the circuit 114 including an auxiliary, low frequency portion 302that may represent built-in test data or the health data of the systemand including a main data, high-frequency portion 304 that maycorrespond to the primary signals associated with the main communicationfunction. In the embodiment shown in FIG. 3, the high frequency portion304 extends over a first bandwidth region, BW1, while the lowerfrequency portion 302 extends over a second bandwidth region, BW2. Theregion BW1 has a first low frequency cut off of f_(low), and the regionBW2 has a high frequency cut off of f_(high), which is less than f_(low)in the illustrated example. Preferably, f_(high) is one or more ordersof magnitude lower than f_(low). In a representative gigabitcommunications link (e.g. Fibre Channel, Gigabit Ethernet, IEEE 1394b,Infiniband, RapidIO, etc.), the high frequency portion 304 may typicallybe spectrally shaped by its coding scheme so that its energy isapproximately zero at frequencies significantly below a basic modulationrate, e.g., below f_(low). Thus, in one representative embodiment, thehigh frequency signal 304 of a 1 gigabit-per-second link may have verylittle energy below 100 MHz and virtually no measurable energy below 10MHz. Correspondingly, f_(high) may be approximately 1 KHz or four ordersof magnitude smaller. These values are provided by way of example,larger and smaller differences in the frequency ranges may be achieved,as well.

On the other hand, the rate at which the low frequency, auxiliary data(e.g., the auxiliary signal 302) typically needs to be exchanged betweennetwork devices or points, in order to determine cable loss and otherrelevant data, may be comparatively modest. For example, a few tens ofbytes of information exchanged at a rate of a few times per second maybe sufficient to maintain all pertinent information about the health ofa link. Thus, a transmission rate for the signal 302 that issubstantially lower than the data transmission rate of the signal 304(e.g. 1 kilobit per second) may be adequate. Such a low-data-rate signalcan be low-pass filtered with a simple filter to a desired low-passlimiting frequency (e.g. 10 KHz), resulting in approximately no effecton Bit Error Rate (BER) performance of the 1 kilobit-per-second healthlink. Such a filtered signal 302 may also have virtually no harmonicenergy above a predetermined frequency (e.g. 1 MHz as shown in theembodiment in FIG. 3). Thus, the primary (data) and auxiliary (health)data signals 302, 304 can be transmitted simultaneously on the samechannel with approximately no measurable interference.

FIG. 4A illustrates a high-speed data signal in a Manchester modulatedformat where each bit of data is represented by at least one bittransition thereby preventing long bitwords of no transition. Manchesterencoding may be self-clocking, which means that accurate synchronizationof a data stream is possible as each bit is transmitted over apredefined time period. Manchester coding is thus characterized by nothaving long periods without bit transitions, thus preventing the loss ofclock synchronization, or bit errors from low-frequency drift.

The high-speed data signal 400 in the illustrated example has apeak-to-peak voltage value 402 that is substantially larger than apeak-to-peak voltage value 404 of a low frequency auxiliary signal 406also shown. In preferred examples the peak-to-peak voltage on theauxiliary data signal 406 is substantially smaller than the peak-to-peakvoltage value for the main data signal 400 by being at least two ordersof magnitude smaller. For example, in typical Fibre Channel or GigabitEthernet applications, the peak-to-peak voltage on the high-speed datasignal is from 0.5 volts to 2 volts. The peak-to-peak value on theauxiliary data signal, however, may be in the microvolt (μV) range, forexample, below 100 μV peak-to-peak for that same Fibre Channel orGigabit Ethernet application.

In fact, one can determine the theoretical value for the voltage for theauxiliary signal, as follows. A receiver consisting of a 50-ohmtermination resistor (R) may produce an RMS noise voltage of:ν_(N)=√{square root over (4kTBR)}=√{square root over(4(1.38×10⁻²³)(300)(1000)(50))}{square root over(4(1.38×10⁻²³)(300)(1000)(50))}{square root over(4(1.38×10⁻²³)(300)(1000)(50))}{square root over(4(1.38×10⁻²³)(300)(1000)(50))}=30 nV_(RMS)  (Eq. 1)Here, k is Avogadro's number, T is temperature in ° K, and B is thebandwidth of the auxiliary signal, BW2, in this instance 1 KHz.

The termination resistor is typically followed by a low-noise amplifier(LNA) which has its own noise that it adds to the signal and which isusually expressed as a Noise Figure (in dB). The Noise Figure expressesthe additional amplifier noise as a ratio to the resistor-generatednoise. A 6-dB Noise Figure would indicate that total noise at theamplifier would be twice the noise given in Eq. 1.

Since 6-dB is a conservative estimate for an amplifier Noise Figure, theworst-case noise can be computed to be around 60 nV_(RMS), in theparticular example above. Multiplying this number by a factor of 10 toproduce a Signal-to-Noise Ratio (SNR) that produces a good Bit ErrorRate (BER), the minimum auxiliary signal peak-to-peak voltage would beapproximately 600 nV_(peak-to-peak). Thus, upping this healthinformation modulation depth to as high as 10 μV still results in aminiscule signal compared to the main communications channel amplitudeof approximately 1 V_(peak-to-peak).

In any event, Equation 1 above confirms that the noise on the auxiliarychannel is sufficiently low that the channel may be used withpeak-to-peak voltage values orders of magnitude lower than that of themain data signal.

To communicate both the auxiliary signal 406 and the main data signal400, the latter may be modulated with the low frequency envelope of theformer to produce the combined signal shown in FIG. 4B. In theillustrated example, the auxiliary data signal is represented byManchester health bits modulating the main data signal, as may beachieved via the combiner device 114 of FIG. 1.

FIGS. 5A-5C illustrate an example technique for removing the auxiliarysignal from a modulated high-speed data signal 500 comprising a highvoltage portion 502 and a low voltage portion 504. FIG. 5A illustratesthe modulated high-speed data signal as depicted in FIG. 4B. FIG. 5Billustrates a rectified waveform version after the modulated high-speeddata signal has been rectified to remove the low voltage portion 504. Asdepicted in FIG. 5B, although the modulated data signal has beenrectified, there are still high frequency components in the waveform, inparticular the high frequency components of the high-speed data portionof the signal. It is also apparent that the rectified signal has arather large signal-to-noise ratio for the auxiliary signals due to thelarger voltage values on high-speed data signal. FIG. 5C (signal 506)represents the rectified data signal of FIG. 5B, after passing through alow pass filter, such as the filter 126 in FIG. 2. As shown, therectified, filter signal of FIG. 5C contains the original modulatedauxiliary information for analysis.

The auxiliary signal may contain information useful for assessing thehealth of a network, such as the built-in test information describedabove. In some examples, the auxiliary signal may be used as part of atime-domain reflectometry (TDR) system capable of determining where inan electrical network fault conditions are occurring by measuringreflections on a transmission line.

FIG. 6 illustrates portions of an example network transceiver 600 thatin a first mode is capable of performing a TDR built-in test for signalloss on a network having a transmission line 602, and in a second modeis capable of sending main data, e.g., high-speed data, modulated withan auxiliary, low speed envelope, which may or may not contain thatobtained TDR data. The transceiver includes a microprocessor 603 and RAM604 operatively coupled to a bus 605 and to a built-in test stage 606and an output stage 608. The stage 606 contains a variable delay device610 for controlling the production of TDR pulse signals to betransmitted during the built-in test mode. The variably delay device 610may comprise a bit counter and digital comparator similar to thevariable delay assembly described in U.S. Publication No. 2005/0110979,entitled “Optical Time Domain Reflectometer and Method Using the Same,”incorporated herein by reference. In the illustrated example of FIG. 6,the delay device 610 is coupled to and drives a signal source 612 of thestage 606, which produces the TDR pulses. In the illustrated example,the signal source 612 is coupled to a switch 613 whose state iscontrolled by the microprocessor 603 for selectively transmitting theTDR pulses or main data from stage 608 depending on the operation modefor the device 600. During a built-in test mode, the switch 613 passesthe TDR pulses from the signal source 612, for example. The output fromthe switch 613 is coupled to a splitter stage 614 operative fortransmitting the signal from the splitter 613 onto the line 602 and forreceiving and isolating reflected signals from the line 602, such asreflected pulses.

Under TDR built-in test mode, the signal source 612 produces very narrowpulses (for example, on the order of 1 ns—nanosecond), which, forexample, may be spaced apart by a repetition rate (frequency) on theorder of the round trip time between known network devices, for example,the nearest network device coupled to the line 602. Both the pulse widthand the repetition rate of the TDR pulses may be determined by thevariable delay circuit 610 under controller of the microprocessor 603.As the narrow pulses travel down line 602, in addition to line lossattenuation, a portion of those pulses will be reflected back toward thetransceiver 600 by impedance discontinuities in the network, whichresults in less signal being transmitted to the load (e.g., remotedevice 625). These reflections are often triggered by the presence of anetwork device, but also will occur due to faults in the transmissionline 602 itself.

In the built-in test mode, the stage 606 is capable of receiving thesereflected signals to the splitter 614 which couples them to a sample andhold circuit 616. The variable delay device 610 is coupled to the sampleand hold device 616 in the illustrated example and communicates timinginformation to the device 616, such as the time elapsed between TDRpulses or the time between a TDR pulse and a received reflected pulse.Preferably, the sample and hold device 616 has a capture time of one 1ns or less for resolving the reflected signals, which would have pulsewidths on the order of or longer than the original TDR pulses. In theillustrated example, the device 616 samples and holds data collected forthe reflected signals and provides that data to an analog to digitalconverter 618 for communication to the microprocessor 603.

In this way, the device 616 may be synchronized with the timing of theTDR pulses for accurate assessment of the location and thus the sourceof the reflected signals. Based on the timing of the reflected signal,the timing of the original TDR pulses, and the time delay therebetween,the microprocessor 603 may determine the physical position of a fault623 on the line 602 as well as that of the remote device 625, both ofwhich could produce line reflections to the device in some examples.Using known techniques, the microprocessor 603 may differentiate betweenthe different reflections, those due to network devices or connectorsand those due to faults in the line. Correspondingly, that informationmay be stored at the computer-readable storage 620 and/or provided to anoutput device or controller via interface 622.

In some examples, by using a low-frequency, or low-repetition rate, TDRsignal, the system 600 may be able to withstand large signal losses,e.g., 20 dB or more, and still provide adequate identification of thesource of the signal loss. By way of example, not limitation, a systemhaving a 50 ft cable, and a 100 ns pulse round trip time, may have aninitial variable delay set to 0.5 ns. A TDR pulse would be sent, areflection sampled at the 0.5 ns delay, and the result stored. Thevariable delay could then be set to 1 ns, a pulse sent, and a samplemade after the 1 ns delay. This continual sampling and holding could bemade with incremental 0.5 ns changes to the variable delay, until thesampling stores a signal above a threshold power. Eventually, areflected signal will be received and the corresponding delay recordedand associated with a physical length along the line. For example, asignal received from a 22 ns delay may correspond to a reflectionoriginating from a point 11 ft down the line. Of course, it will beunderstood that this is just an example. It will also be understood thatdifferent TDR computational techniques may be used for the built-intesting.

Once the TDR information has been obtained, that data may becommunicated to an auxiliary data source 624 also coupled to the bus605. The source 624 may use this TDR data as auxiliary built-in testdata that is combined, in a modulating manner, with the main datasignals from a source 626 and via a combining circuit 628, as describedabove. The output from the circuit 628 (e.g., a signal like thatillustrated in FIG. 4B) is provided to the switch 613 for communicatingto the splitter 614 when the device 600 is in a second, or mainsignaling mode. That is the TDR operation occurs separately from maindata signal operation.

While FIG. 6 shows an example implementation of a built-in testing on anelectrical network, persons of ordinary skill in the art will appreciatethat the techniques described herein may be used in other configurationsand in other applications beyond TDR.

Although certain apparatus constructed in accordance with the teachingsof the invention have been described herein, the scope of coverage ofthis patent is not limited thereto. On the contrary, this patent coversall embodiments of the teachings of the invention fairly falling withinthe scope of the appended claims either literally or under the doctrineof equivalents.

1. An apparatus for providing auxiliary channel communication on anelectrical signal-based network, the apparatus comprising: an electricalsignal source adapted to provide a high-speed data signal extending overa high frequency range and having a first maximum peak-to-peak value,the signal source adapted to provide an auxiliary data signal extendingover a low frequency range below the high frequency range and having asecond maximum peak-to-peak value smaller than the first maximumpeak-to-peak value, wherein the second maximum peak-to-peak value is atleast two orders of magnitude smaller than the first maximumpeak-to-peak value, the second maximum peak-to-peak value is larger thanat least twice a RMS noise voltage, ν_(n), wherein ν_(n) is expressed byν_(n)=√{square root over (4kTBR)}  wherein k is Avogadro's number, T istemperature in K, and B is the bandwidth of the low frequency range; anda controller coupled to the signal source for controlling the signalsource to produce the high-speed data signal and for modulating thehigh-speed data signal with the auxiliary data signal.
 2. The apparatusof claim 1, wherein the high frequency range of the high-speed datasignal extends from a frequency of at least 10 MHz or higher, andwherein the low frequency range of the auxiliary signal is below 10 MHz.3. The apparatus of claim 2, wherein the low frequency range is at least1 kHz or below.
 4. The apparatus of claim 1, wherein the high frequencyrange of the high-speed data signal has a low cut-off frequency, andwherein the low frequency range of the auxiliary data signal has a highcut-off frequency that is at least two orders of magnitude lower thanthe low cut-off frequency.
 5. The apparatus of claim 1, wherein theauxiliary data signal has an upper voltage portion and a lower voltageportion, the apparatus further comprising a receiver comprising: arectifying circuit for removing the lower voltage portion from theauxiliary data signal and producing a rectified auxiliary data signal; afiltering circuit coupled to the rectifying circuit for filtering thehigh speed data signal from the rectified auxiliary data signal; and asecond controller for assessing the filtered, rectified auxiliary datasignal.
 6. The apparatus of claim 5, wherein the rectifying circuitcomprises a rectifying diode, and wherein the filtering circuit is alow-noise amplifier circuit.
 7. The apparatus of claim 1, wherein theauxiliary data signal includes health information for the electricalsignal-based network.
 8. The apparatus of claim 7, wherein the auxiliarydata signal includes data for a transmitted power level of theelectrical network.
 9. The apparatus of claim 1, wherein the high-speeddata signal and the auxiliary data signal are Manchester modulated datasignals.
 10. An apparatus for testing an electrical signal-based networkcapable of transmitting a high-speed data signal extending over a highfrequency range and having a first maximum peak-to-peak value, theapparatus comprising: a transmitter having a signal source adapted tomodulate the high-speed data signal with an auxiliary data signalextending over a low frequency range below the high frequency range andhaving a second maximum peak-to-peak value, wherein the second maximumpeak-to-peak value is at least two orders of magnitude smaller than thefirst maximum peak-to-peak value, the second maximum peak-to-peak valueis larger than at least twice a RMS noise voltage, ν_(n), whereinν_(n)is expressed byν_(n)=√{square root over (4kTBR)}  wherein k is Avogadro's number, T istemperature in K, and B is the bandwidth of the low frequency range, theauxiliary data signal comprising operational data of the transmitter;and an analyzing circuit coupled to receive the modulated high-speeddata signal from the signal source and adapted to separately analyze theauxiliary data signal from the modulated high-speed data signal forassessing the operational data.
 11. The apparatus of claim 10, whereinthe high frequency range of the high-speed data signal extends from afrequency of at least 10 MHz or higher, and wherein the low frequencyrange of the auxiliary signal is at least 1 kHz.
 12. The apparatus ofclaim 10, wherein the high frequency range of the high-speed data signalhas a low cut-off frequency, and wherein the low frequency range of theauxiliary data signal has a high cut-off frequency that is at least twoorders of magnitude lower than the low cut-off frequency.
 13. Theapparatus of claim 10, wherein the auxiliary data signal has an uppervoltage portion and a lower voltage portion, the analyzing circuitfurther comprising: a rectifying circuit for removing the lower voltageportion from the auxiliary data signal and producing a rectifiedauxiliary data signal; and a filtering circuit coupled to the rectifyingcircuit for filtering the high speed data signal from the rectifiedauxiliary data signal.
 14. A method for testing an electricalsignal-based network capable of transmitting a high-speed data signalextending over a high frequency range and having a first maximumpeak-to-peak value, the method comprising: adapting a signal source tomodulate the high-speed data signal with an auxiliary data signalextending over a low frequency range below the high frequency range andhaving a second maximum peak-to-peak value, wherein the second maximumpeak-to-peak value is at least two orders of magnitude smaller than thefirst maximum peak-to-peak value, the second maximum peak-to-peak valueis larger than al least twice a RMS noise voltage, ν_(n), wherein ν_(n)is expressed byν_(n)=√{square root over (4kTBR)}  wherein k is Avogadro's number, T istemperature in K, and B is the bandwidth of the low frequency range, theauxiliary data signal comprising operational data of a transmitter; andproviding an analyzing circuit adapted to separately analyze theauxiliary data signal from the modulated high-speed data signal forassessing the operational data.
 15. The method of claim 14, wherein thehigh frequency range of the high-speed data signal extends from afrequency of at least 10 MHz or higher, and wherein the low frequencyrange of the auxiliary signal is at least 1 kHz.
 16. The method of claim14, wherein the high frequency range of the high-speed data signal has alow cut-off frequency, and wherein the low frequency range of theauxiliary data signal has a high cut-off frequency that is at least twoorders of magnitude lower than the low cut-off frequency.
 17. The methodof claim 14, wherein the auxiliary data signal has an upper voltageportion and a lower voltage portion, the method further comprising:providing a rectifying circuit for removing the lower voltage portionfrom the auxiliary data signal and producing a rectified auxiliary datasignal; and providing a filtering circuit coupled to the rectifyingcircuit for filtering the high speed data signal from the rectifiedauxiliary data signal.